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Rigorous Analytical Expressions for Electromagnetic Parameters of Transmission Lines: Coupled Sliced Coaxial Cable
A set of accurate closedform formulas for primary parameter matrices and even and oddmode impedances for coupled sliced coaxial cables
Technical Feature
Rigorous Analytical Expressions for Electromagnetic Parameters of Transmission Lines: Coupled Sliced Coaxial Cable
This article is a continuation of a previous article that appeared in Microwave Journal and is the first part in the development of accurate closedform formulas for the primary parameters (inductance [L] and capacitance [C] matrices) and impedances (Z_{oe} , Z_{oo} ) of the even and oddmodes for several configurations of transmission lines (sliced coaxial cables, symmetrical band lines and split ring lines). The analytical expressions, deduced from rigorous analysis by the finite element method (FEM)^{1,2} , method of moment (MoM)^{3} and curvefitting techniques, can be easily implemented in CAD simulation tools to design components for wireless communication. This study presents accurate and suitable general expressions for all coupled sliced coaxial cables with a wide range of cut depths and an outer to inner conductor radius ratio between 1.4 and 15. The results of the design of an RF coupler using coupled sliced coaxial cables are presented.
N. Benahmed and M. Feham
University of Tlemcen
Tlemcen, Algeria

Fig. 1 Crosssection of the coupled line with sliced coaxial cables. 
A directional coupler, using a coupled line composed of two shaped cut coaxial cables, has been analyzed and tested by Djordjevic, et al.^{3} This type of coupler shows excellent performance in terms of high directivity, very low SWR, good isolation, excellent electromagnetic interference (EMI) shielding, high power handling capability, extremely low cost due to the use of commercial semirigid coaxial cables and elimination of a mechanical housing.^{4,5}
The electrical properties of a lossless coupler using a TEMmode coupled line can be described in terms of even (Z_{oe} ) and odd (Z_{oo} ) mode impedances, and its primary parameter matrices [L] and [C],^{2}
where
L_{o} = proper inductance of the isolated line
C_{o} = capacitance of the isolated line
M = mutual inductance of the coupled line
g = coupling capacitance of the coupled line
The crosssection of a coupled line with sliced coaxial cables is shown in Figure 1 .
The cable is assumed to be lossless with an inner conductor of radius R_{c} and an outer conductor of radius R_{b} .
A material with dielectric constant e_{r} fills the inside of the cable. A portion of each cable is cut out and two of these cut cables are used to form the coupled line. The cut depth is represented by h on the crosssection and
H. An, et al. presented formulas only for even and oddmode characteristic impedances of the coupled line with a sliced coaxial cable.^{6} Their expressions, deduced from a FEM analysis, are valid in the ranges
0 ≤ u ≤ 0.99
and
In this article, formulas are offered for the even and oddmode characteristic impedances and also the [L] and [C] matrices of the coupled line with sliced coaxial cables having an outer to inner conductor radius ratio
and a cut depth
0 ≤ u ≤ 0.99
These formulas are deduced from an analysis using two coherent numerical methods: FEM and MoM.




Fig. 2 Even and oddmode characteristic impedances as a function of cut depth.  Fig. 4 Evenmode characteristic impedance as a function of cut depth with conductor radius ratio as a parameter.  Fig. 6 Inductance as a function of cut depth with conductor radius ratio as a parameter.  Fig. 8 Capacitance as a function of cut depth with conductor radius ratio as a parameter. 




Fig. 3 Even and oddmode characteristic impedances as a function of conductor radius ratio.  Fig. 5 Oddmode characteristic impedance as a function of cut depth with conductor radius ratio as a parameter.  Fig. 7 Mutual inductance as a function of cut depth with conductor radius ratio as a parameter.  Fig. 9 Coupling capacitance as a function of cut depth with conductor radius ratio as a parameter. 
Numerical Results
In order to validate the numerical results, a structure with an outer conductor radius R_{b} = 1.49 mm, an inner conductor radius R_{c} = 0.255 mm and a permittivity e_{r} = 1 is studied. Figures 2 and 3 show a comparison between the FEM and MoM results. Through this comparison, it appears that a good agreement is obtained between the two numerical methods.
The FEM results of the even and oddmode characteristic impedances and elements of the [L] and [C] matrices, for different values of conductor radius, are shown in Figures 4 to 7 . Oddmode characteristic impedance and mutual inductance as a function of cut depth is shown in Figures 8 and 9 .
Derivation of Analytical Expressions
Characteristic Impedances
By curvefitting to the FEM results, it is found that the evenmode characteristic impedance Z_{oe} of the coupled line can be expressed by
Z_{oe} = Z_{o} + b_{1} u + b_{2} u^{2} + b_{3} u^{3} (1)
where
Z_{o} = 31.626 + 45.864r  5.623r^{2} + 0.354r^{3}  0.0085 r^{4}
b_{1} = 0.862  2.982r + 1.841r^{2}  0.148r^{3} + 0.0039r^{4}
b_{2} = 6.862 + 24.858r  8.728r^{2} + 0.690r^{3}  0.018r^{4}
b_{3} = 20.311 + 4.254r + 4.289r^{2}  0.404r^{3} + 0.011r^{4}
and the oddmode characteristic impedance (Z_{oo} ) is given by
where
a_{1} = 37.78 + 50.089r  6.398r^{2} + 0.417r^{3}  0.01r^{4}
a_{2} = 310.831  366.622r + 47.908r^{2}  3.263r^{3} + 0.083r^{4}
u_{o} = 1.407  0.017r + 0.0024r^{2}  1.507 10^{4} r^{3} + 3.554 10^{6} r^{4}
du = 0.153 + 0.0045r  11 10^{4} r^{2} + 8.483 10^{5} r^{3} 2.21 10^{6} r^{4}
Appendix A shows a comparison between the analytical results and those of the literature^{6} for different values of the cut depth.
Through this comparison, it appears that a good correlation is obtained between these analytical results and those already published.
Inductance Matrix Per Unit Length
The proper and mutual inductances of the coupled line are given by Equations 3 and 4, respectively.
for 1.4 ≤ r ≤ 6
L_{o1} = 436.432  366.538e^{(r1.4)/3.1212}
A = 27.802  23.536e^{(r1.4)/2.5891}
v = 0.8115  0.12441e^{(r2)/2.4837}
u_{o} = 0.7396  0.140e^{(r1.4)/1.9622}
for 6 < r ≤ 15
L_{o1} = 585.577  437.491e^{(r1.4)/6.3446}
A = 31.106  21.724e^{(r2)/3.5100}
v = 0.84299  0.153e^{(r2)/2.7368}
u^{o} = 0.75584  0.11663e^{(r2)/2.7368}
M_{o1} = 6.41196  9.790r + 2.229r^{2}  0.2574r^{3} + 0.01429r^{4}  3.04337 10^{4} r^{5}
A = 41.40657 + 28.596r  1.88142r^{2} + 0.05831r^{3}
v = 0.35977 + 0.12777e^{(r1.4)/2.0479} + 0.12901e^{(r1.4)/13.71907}
for 1.4 ≤ r ≤ 9
u_{o} = 1.05019 + 0.32048e^{(r1.4)/0.748}
for 9 < r ≤ 15
u_{o} = 0.52158 + 0.12912r  0.01035r^{2} + 2.81944 10^{4} r^{3}
Capacitance Matrix Per Unit Length
Equations 5 and 6 give the proper and coupling capacitance of the coupled line with sliced coaxial cables, respectively.
A = 20.49514 + 97.89073e^{(r1.4)/0.4082} + 44.34461e^{(r1.4)/3.25406}
B_{1} = 14.38252 + 8.21613r  2.11056r^{2} + 0.26037r^{3}  0.01521r^{4} + 3.38153 10^{4} r^{5}
B_{2} = 8.41414 + 3.64185r  1.00611r^{2} + 0.08854r^{3}  0.00249r^{4}  9.01856 10^{6} r^{5}
B_{3} = 84.99654 + 11.33169r  0.24693r^{2}  0.06647r^{3} + 0.00411r^{4}  3.29262 10^{5} r^{5}
B_{4} = 14.88927 + 61.27891e^{(r0.99433)/19.259} + 67.37928e^{(r0.99443)/1.32918}
for 1.4 ≤ r ≤ 7
g_{1} = 18.10709 + 18.82952r  8.41344r^{2} + 1.85398r^{3}  0.19828r^{4} + 0.0082r^{5}
u_{o} = 1.40387  0.36507r + 0.17369r^{2}  0.04274r^{3} + 0.00525r^{4}  2.54706 10^{4} r^{5}
v = 1.01161  0.75568r + 0.37576r^{2}  0.09433r^{3} + 0.01168r^{4}  5.67111 10^{4} r^{5}
A = 386.55698  445.76406r + 223.82846r^{2}  56.34847r^{3} + 6.99263r^{4}  0.34033r^{5}
for 7 < r ≤ 15
g_{1} = 0.47174  0.47528e^{(r7)/4.4014}
u_{o} = 4.00282  1.24415r + 0.21668r^{2}  0.01879r^{3} + 8.08443 10^{4} r^{4}  1.37917 10^{5} r^{5}
A = 7.12991 + 16.23608e^{(r7)/9.6403} + 6.11658e^{(r7)/1.78277}
Appendix B shows a comparison between the analytical and numerical results for R_{c} = 0.255 mm, R_{b} = 0.51 mm, u = 0.7 and e_{r} = 1.
The above expressions are valid for airlines. For dielectric filled coaxial lines with dielectric constant of e_{r} , the expressions are
C'_{o} = C_{o} e_{r}
and
L = L_{o}
The relative errors between numerical and analytical results are less than 2 peR_{c} ent over a wide range, indicating good accuracy of the closedform expressions for the coupled line with sliced coaxial cables.
Directional Coupler Design
Figure 10 shows the structure of a directional coupler using the coupled line with cut coaxial cables. The parameters of this coupler, operating in the 300 MHz to 3 GHz frequency range, using the coupled line with sliced coaxial cable, are
Z_{oe} = 48.35 W
Z_{oo} = 36.03 W
The features of the coupled line obtained from the proposed formulas are
 Outer conductor radius R_{b} = 0.51 mm
 Inner conductor radius R_{c} = 0.255 mm
 Dielectric constant e_{r} = 1
 Conductivity s = 5.65 10^{7} (Wm)^{1}
 Coupler length 1 = 40 mm
The simulated response of the designed coupler is shown in Figure 11 .
In the frequency range 0.6 to 3 GHz, the coupling is less than 22 dB and the minimum directivity is 17 dB, which permit the designed coupler to have good coupling and isolation over a large frequency range.


Fig. 10 Diagram of the directional coupler.  Fig. 11 Coupling S_{12}  and isolation S_{14}  of the directional coupler. 
Conclusion
This article presents a set of accurate closedform formulas for the primary parameter ([L], [C]) matrices and the impedances (Z_{oe} , Z_{oo} ) of the even and oddmodes for the coupled sliced coaxial cables. These expressions deduced from the FEM and MoM are valid in a wide range of outer to inner conductor radius ratios.
As an application of this study, a directional coupler, operating over a broad frequency range using the coaxial coupled line, has been successfully designed.
APPENDIX A  
u  Even Mode  Odd Mode  
Z_{oe} ( W)  Z_{oe} ( W)  Z_{oo} ( W)  Z_{oo} ( W)  
0.2  76.0745  75.29  75.2165  74.28 
0.4  78.7149  78.43  74.3151  73.33 
0.6  84.5746  84.15  71.0909  71.40 
0.8  96.4674  97.2549  59.7603  58.095 
APPENDIX B  
Electromagnetic  FEM  Analytical  Errors 
L_{o} (nH/m)  144.2  142.178  1.422 
M (nH/m)  19.96  19.618  1.743 
C_{o} (pF/m)  77.68  78.8047  1.447 
g (pF/m)  11.12  10.9271  1.7653 
Z_{oe} (W)  49.11  48.3513  1.569 
Z_{oo} (W)  36.55  36.034  1.431 
References
1. N. Benahmed, M. Feham and M. Kameche, "Finite Element Analysis of Planar Couplers," Applied Microwave & Wireless , Vol. 12, No. 10, October 2000.
2. N. Benahmed and M. Feham, "Finite Element Analysis of RF Couplers with Sliced Coaxial Cable," Microwave Journal , Vol. 2, No. 2, November 2000, pp. 106120.
3. A.R. Djordjevic, D. Darc, M.C. Goran and T.K. Sarkan, Circuit Analysis Models for Multiconductors Transmission Lines , Artech House Inc., Norwood, MA, 1997.
4. H. An, O. Monti, R.G. Bossio and K. Wu, "A Novel Type of Low Cost High Performance Coaxial Cables Coupler," 25th European Microwave Conference , 1995.
5. H. An, R.G. Bossio and K. Wu, "Ultrawide Band Directional Couplers with Coaxial Cable," Canadian Conf. Electr. and Comp. Eng ., 1995.
6. H. An, T. Wang, R.G. Bossio and K. Wu, "Accurate Closedform Expression for Characteristic Impedance of Coupledline with Sliced Coaxial Cable," IEE Proceedings , 1995.