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Technical Feature
A Large Bandwidth Tshaped Microstripfed Ground Plane Slot Antenna
The characteristics of a Tshaped microstrip feeding a ground plane slot antenna have been analyzed using the finite difference time domain (FDTD) method. The impedance and bandwidth of the proposed antenna depend highly on the design parameters. The radiation resistance has a low value. The measured bandwidth is approximately 39.6 percent for S_{11}  ≥ 10 dB.
YongWoong Jang
College of Keukdong
Eumsung, Korea
JeongChull Yoon
ACE Technology Co.
Chatsworth, CA
HoSub Shin
National University of Chungbuk
Chungbuk, Korea
Microstrip antennas offer the advantages of thin profile, light weight, low cost, conformability to a shaped surface and compatibility with integrated circuitry. The slot antenna has been investigated since the 1940s,^{1} and is treated in many electromagnetic text books.^{2,3} The major drawback of a microstrip antenna, in its basic form, is its inherently narrow bandwidth. This is a major obstacle to its wide application.
In a conventional microstriplinefed slot antenna, a narrow rectangular slot is cut in the ground plane, and the slot is excited by a microstrip feedline with either a short^{4} or an open^{5} termination. With this feed configuration, a good impedance match has been achieved for a narrow slot, and an impedance bandwidth of approximately 20 percent has been obtained.^{6} However, as the width of the slot increases, the radiation resistance of the slot antenna increases proportionately. This, in turn, reduces the impedance bandwidth of the antenna even though the size of the slot is larger.^{7} Shum, et al.^{8} have shown the possibility of increasing the bandwidth of the wide slot antenna by terminating the open end of the feedline within the width of the slot; however, substantial bandwidth improvement has not been achieved with this approach.
In this article, the impedance of the Tshaped microstrip feedline structure and the conventional feeding structure have been analyzed using the FDTD method. Good impedance match is obtained with a conventional feeding structure, only for narrow slots. However, a Tshaped feedline is able to match the input impedance for a narrow as well as a wide slot antenna. When the Tshaped feedline is used, the bandwidth is extended proportionately to the slot width and the radiation resistance has a low value. The characteristics of a printed slot antenna fed with a Tshaped microstrip line have been studied. A bandwidth wider than for the conventional feed has been obtained. From these results, an antenna having a broad bandwidth was designed, fabricated and measured.
FDTD Formulation
The FDTD method is formulated by discretizing Maxwell's curl equations over a finite volume and approximating the derivatives with central difference approximations. These finite difference time domain approximate equations contain a secondorder error in both space and time steps. According to Yee's notation,^{9} the space point in the FDTS cell is (iD x, jDy, kDz), the time increment is nDt and the arbitrary function is represented as F(iD x, jDy, kDz, nDt). In the analysis of the microstrip slot antenna design, the Mur's absorbing boundary condition^{10} was applied. The time domain value, which is calculated by a finite time domain method,^{11} is Fouriertransformed and the response value in the frequency domain can be calculated. Since the microstrip feedline is an open stub, the microstrip antenna is a oneport circuit. Therefore, the reflection coefficient S_{11} of the microstrip antenna is given by
where
V_{1} ^{ref(t)} = reflected voltage
V_{1} ^{inc(t)} = incident voltage
F = Fourier transform notation
From the calculated reflection coefficient, the voltage standing wave ration (VSWR) can be obtained from
The percentage bandwidth of the antenna was determined from the impedance data. From now on the term bandwidth will refer to percentage bandwidth unless otherwise specified. The bandwidth is defined as
where
f_{r} = resonance frequency
f_{r1} and f_{r2} = frequencies for which the magnitude of the reflection coefficient is less than or equal to 1/3 (corresponding to a VSWR ≤ 2)
The electric field of the farfield patterns can be calculated as
where
k = propagation constant
E_{m} = electric field at the slot
W = slot width
L = slot length
Antenna Structure and Simulation Results

Fig. 1 Structure of the slot antenna showing the design parameters. 
The structure of the proposed antenna, as shown in Figure 1 , consists of the slot radiator and a Tshaped feedline. A Tshaped microstrip feedline is proposed to match the input impedance for narrow as well as wide slot antennas. When a Tshaped feedline is used, the bandwidth can be broadened proportionately to the slot width with good impedance matching. This type of antenna is better than the conventional feedline structure. The substrate used has a dielectric constant of 4.3 and a thickness of 1.0 mm. The slot is l_{s} and its width is W_{s} . The length of the horizontal branch of the T is l_{d} . The offset is the distance between the slot center and the center of the microstrip line; W_{f} is the width of the feedline. To analyze the antenna correctly, Dy and Dx are chosen so that an integral number of nodes fit the feedline and slot exactly. Dz is chosen so that an integral number of nodes fit the thickness h of the substrate exactly. The sizes of the space cells are Dx = 0.3214 mm, Dy = 0.25 mm, Dz = 0.333 mm. The total analysis space is composed of 280 x 360 x 43 cells in the x, y, z directions, respectively. The size of the antenna elements used in the analysis are l_{s} = 156 Dx, W_{s} = 64 Dy, l_{d} = 110 Dx, offset = 18 Dy, W_{f} = 6 Dx. In order to calculate the input Sparameters, a standard technique of time gating the signal on the microstrip line is used to separate the incident and reflected waveforms. The Sparameters are obtained from the ratio of the Fourier transforms of these waveforms. The simulation is allowed to continue until the energy reflected from the resonant cavity toward the source has been reduced to a negligible level. Stopping the run too early results in ripples on the calculated Sparameters.

Fig. 2 E_{z} field component after 1000 time steps (steady state). 
Figure 2 shows the threedimensional E_{z} component of the electric field as the timevarying pulse has reached a steady state. The time step is 1.9 ps to satisfy the Courant stability condition.^{12} The pulse width is 32 time steps. The Gaussian pulse is excited just underneath the dielectric interface of the antenna.

Fig. 3 Normalized radiation resistance (to 50 W) for a slot antenna with conventional and Tshaped microstrip feeds. 
Figure 3 shows the comparison of the normalized (to 50 W) radiation resistance of a slot antenna with the proposed and the conventional feeding structures. The conventional centerfed transverse slot antenna has a large value of radiation impedance. This case is good for the impedance matching of a narrow slot antenna only. But a Tshaped feedline is able to match the input impedance of not only a narrow but also a wide slot antenna. When the Tshaped feedline is used, the radiation resistance does not change from its low value (the normalized resistance value is approximately 1.0) as a function of the slot width.
The characteristics of the antenna are sensitive to the design parameters (l_{s} , W_{s} , l_{d} , offset, W_{f} ). The input impedance, return loss and radiation pattern in the frequency domain are calculated by taking the Fourier transform of the time domain results.
With the other parameters fixed, when the width of the slot is varied from 8 to 32 mm with a constant cell size Dy = 0.25 mm, the normalized impedance results are shown in Figure 4 . When W_{s} is 16 mm, the normalized radiation resistance and reactance are approximately 1.0 and zero, respectively, at the center frequency of 2.3 GHz. Good impedance matching is obtained for W_{s} = 16 mm at the center frequency of 2.3 GHz.


Fig. 4 Normalized input impedance (to 50 W) as a function of the slot width and frequency; (a) resistance and (b) reactance.  Fig. 5 Normalized (to 50 W) input impedance as a function of offset and frequency; (a) resistance and (b) reactance. 
With the other design parameters fixed, when the offset position is varied from 0 to 5.5 mm, the normalized impedance results are shown in Figure 5 . When the offset is 0 mm, the normalized radiation resistance is approximately 3.5 at 2.3 GHz. However, when the offset is 4.5 mm, the normalized radiation resistance and reactance are about 1.0 and 0, respectively, at the center frequency. This means that the antenna is resonant at the center frequency of 2.3 GHz for an offset = 4.5 mm.
Table 1 shows the optimized design parameters of the proposed structures and their bandwidth as a function of the slot width.
Table 1  
W_{s}  I_{d}  Offset  Offset/W_{s}  BW [MHz] 
4  38.3  1.01  0.253  310(13.5) 
6  37.5  1.58  0.263  421 (18.3) 
8  37.0  2.16  0.270  515 (22.4) 
10  36.0  2.70  0.270  554 (24.1) 
12  36.0  3.24  0.270  619 (26.9) 
14  35.5  3.89  0.278  741 (32.2) 
16  35.5  4.50  0.281  900 (39.1) 
18  35.0  5.10  0.283  925 (40.2) 
20  34.5  5.66  0.283  943 (41.0) 
22  34.0  6.23  0.284  957 (41.6) 
32  31.0  10.00  0.313  1050 (45.7) 
Experimental Results
The proposed antenna was fabricated using an FR4 substrate (e_{r} = 4.3, h = 1.0 mm) and the ground plane size of the twoelement microstrip slot antenna array is 230 mm x 120 mm. The measurements were performed with an HP8510B network analyzer.
Figure 6 shows the measured impedance locus. The input impedance of the antenna exhibits a broad bandwidth characteristic, which is to be contrasted with the narrow band characteristic of the conventional microstriplinefed structure. The measured results are in good agreement with the calculated results.
The calculated and measured return loss of this antenna are compared in Figure 7 . The measured results are in good agreement with the FDTD results. The measured bandwidth of the antenna is 1.8 to 2.71 GHz, which is approximately 39.6 percent for S_{11}  ≥ 10 dB, at the center frequency of 2.3 GHz. The measured bandwidth (39.6 percent) is wider than the simulation result (39.1 percent).
Figure 8 shows the experimental radiation pattern in the xz plane at f = 2.3 GHz. After calibration using a horn antenna, the far field radiation pattern was measured. The beamwidth is approximately 70°.



Fig. 6 Measured input impedance.  Fig. 7 Return loss of the proposed antenna.  Fig. 8 Measured radiation pattern in the xz plane at 2.3 GHz. 
Conclusion
The characteristics of a Tshaped microstriplinefed printed slot antenna are presented. It was found that the bandwidth of the antenna depends highly on the design parameters. The proposed antenna has low radiation resistance and wide band characteristics. The experimental bandwidth is approximately 39.6 percent. This antenna may be useful in broadband antenna arrays.
References
1. H.G. Booker, "Slot Aerials and Their Relation to Complementary Wire Aerials," J. IEE (London) , Part IIIA, Vol. 93, 1946, pp. 620626.
2. Robert E. Collin, Antenna and Radiowave Propagation , McGrawHill, NY, 1985.
3. R.Garg, P. Bhartia, I. Bahl and A. Ittipiboon, Microstrip Design Handbook , Artech House, MA, 2001, Chapter 7.
4. Y. Yoshimura, "A Microstrip Slot Antenna," IEEE Transactions on Microwave Theory and Techniques , Vol. 20, No. 11, November 1972, pp. 760762.
5. D.M. Pozar, "Reciprocity Method of Analysis for Printed Slot and Slotcoupled Microstrip Antennas," IEEE Transactions on Antennas and Propagation , Vol. AP34, December 1986, pp. 14391446.
6. A. Axelrod, M. Kisliuk and J. Maoz, "Broadband Microstripfed Slot Radiator," Microwave Journal , Vol. 32, No. 6, June 1989, pp. 8192.
7. M. Kahrizi, T.K. Sarkar and Z.H.Maricevic, "Analysis of a Wide Radiating Slot in the Ground Plane of a Microstrip Line," IEEE Transactions on Microwave Theory and Techniques , Vol. 41, No. 1, January 1993, pp. 2937.
8. S.M. Shum, K.F. Tong, X. Zhang and K.M. Luk, "FDTD Modeling of Microstriplinefed Wide Slot Antenna," Microwave Optical Technology Letters , Vol. 10, No. 10, October 1995, pp. 118120.
9. K.S. Yee, "Numerical Solution of Initial Boundaryvalue Problems Involving Maxwell's Equations in Isotropic Media," IEEE Transactions on Antennas and Propagation , May 1966, Vol. 14, pp. 302307.
10. G. Mur, "Absorbing Boundary Conditions for the Finitedifference Approximation of the Timedomain Electromagneticfield Equation," IEEE Transactions on Electromagnetic Compatibility , Vol. 23, No. 4, November 1981, pp. 377382.
11. D.M. Sheen, S.M. Ali, M.D. Abouzahra and J.A. Kong, "Application of Threedimensional Finitedifference Timedomain Method to the Analysis of Planar Microstrip Circuits," IEEE Transactions on Microwave Theory and Techniques , Vol. 38, No. 7, July 1990, pp. 849857.
12. A. Taflove and M.E. Brodwin, "Numerical Solution of Steadystate Electromagnetic Scattering Problems Using the Timedependent Maxwell's Equations," IEEE Transactions on Microwave Theory and Techniques , Vol. 23, No. 8, August 1975, pp. 623630.
YongWoong Jang received his BS and MS degrees from Myongji University, Seoul, South Korea, in 1989 and 1991, respectively, and his PhD degree from Ajou University, Suwon, South Korea, in 1999. He then became a member of the faculty in the department of electronics communication engineering at the College of Keukdong at Eumsung in Korea. He is now an associate professor. His main areas of interest are antennas, RFsystems and numerical methods in solving electromagnetic problems.
JeongChull Yoon received his BS and MS degrees from Ajou University, Suwon, South Korea, in 1996 and 1998, respectively. From 1998 to 2000 he worked at ACE Technology Co. as a research member. Since 2001 he has been researching at Sam Sung Electromechanic joint stock company. His main areas of interest are antennas, RFsystems and EMI/EMC.
HoSub Shin received his BS and MS degrees in computer and communication engineering from the National University of Chungbuk, South Korea, in 1995 and 1998, respectively. He is currently working toward his PhD degree in computer and communication engineering. His research interest is in the area of numerical analysis and modeling of electromagnetic fields and antenna using FDTD.
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